Variable power communications including rapid switching between coding constellations of various sizes

ABSTRACT

A method of varying the power output of a transmitter. The method includes providing bit-loading information associated with each tone of multiple tones, where the multiple tones include a first set of tones. The method also includes producing, for transmission, on the first set of tones a first set of constellation symbols based upon the bit-loading information. The method also includes producing a second set of constellation symbols for transmission, where there is a difference of n bits between the bit size of the second bit sequence constellation symbol on each tone of the second set of tones and the bit-loading information associated with each tone of the first set of tones, and where n is an integer greater than or equal to 0.

BACKGROUND INFORMATION

There are many reasons for a wired communications device or a wirelesscommunications device to change the power level being used tocommunicate with another device. Possible motivations for changing thepower level may involve a desire to decrease the potential forinterference with other devices or comply with regulatory standardsspecifying a certain power spectral density mask.

Interference among devices is a significant problem in both wirelesscommunications and wired communications networks. In wired networks, theinterference is partly due to the close proximity of cables next to eachother carrying signals at high frequencies and often in a common band.

The problem of interference is particularly bad in wired networks thatwere designed to carry relatively low-frequency, low-power analogsignals, such as voice telephone signals, but are now being used tocarry relatively high frequency and higher power modem signals. FIG. 1 aillustrates a bundle of cables carrying various types of signals ascommonly found in a bundle including cables for telephone signals.

As illustrated in FIG. 1 a, the increasing use of digital subscriberline (DSL) technology to provide relatively high-speed access to theInternet has made the problem of interference in cables carryingtelephone and data signals more common and more likely. Examples of DSLtechnology include HDSL and ADSL. HDSL refers to high-data rate DSL, andADSL refers to asymmetric DSL. In ADSL, the upstream data rate from thesubscriber to the central office is lower than the downstream data ratefrom the central office to the subscriber. A particularly bad form ofinterference in the wired communications context and particularly forDSL communications is referred to as crosstalk.

FIG. 1 b illustrates examples of crosstalk in DSL links. There areseveral types of crosstalk including two typically dominant ones:near-end crosstalk (NE-XT, or NEXT); and far-end crosstalk (FE-XT, orFEXT). In links 100, NE-XT interference is due to signals that aretransmitted in opposite directions and is illustrated by interference103 that is caused by transmitter 102 a to receiver 104 b. In NE-XTinterference the output of a nearby transmitter goes into a nearbyreceiver, and the transmitter and receiver need not be using the sametechnology (e.g, ADSL) to communicate. In the case of FE-XT,interference is due to signals that are transmitted in the samedirection, and again, the transmitters and receiver need not be usingthe same technology (e.g, ADSL) to communicate. FE-XT interference isillustrated by interference 105 that is caused by transmitter 106 a toreceiver 104 b.

‘Self NE-XT’ refers to NE-XT interference that is due to transmittersusing the same technology as the receiver. For example, ADSL modemscause interference to other ADSL modems. ‘Self FE-XT’ refers to FE-XTinterference that is due to transmitters using the same technology asthe receiver. Again, an example would be ADSL modems causinginterference with other ADSL modems.

The nature of self-NEXT and self-FEXT is such that increasing theaverage transmitted power generally does not appreciably change thedistance over which a modem can communicate because crosstalk powerchanges in direct proportion to the average transmitted power. On shortloops, VDSL (very high speed digital subscriber line) modems providehigh bandwidth, but have limited reach due to self-NEXT and self-FEXT.VDSL modems typically transmit data in the 13 Mbps to 55 Mbps range overdistances of about 4500 feet of twisted pair copper wire, but longerranges are also becoming possible and higher data rates may be possibleas well.

Nevertheless, dynamically varying the transmit power for VDSL modems hasbeen discussed at the International Telecommunications Union (ITU). Aproposal that was made involved switching between a full power mode andno power mode and using a secondary control channel to alter modemstate. The proposal suffers from at least two principal defects: 1)sudden changes from no power to full power by one or more modems arelikely to result in other modems losing synchronization (i.e., not‘environmentally friendly’ to other devices trying to communicate) andhaving to ‘re-train’ to regain synchronization; and 2) the switchingmechanism using the secondary control channel is relatively too slow.Furthermore, regaining synchronization is a relatively slow process.Consequently, the problems of changing power quickly and minimizing theadverse effect on other devices are substantial issues that needaddressing with solutions that overcome the deficiencies of the priorart.

SUMMARY

In an embodiment, a method of varying power output for a transmitter isdescribed. The method includes providing bit-loading informationassociated with each tone of multiple tones, where the multiple tonesinclude a first set of tones. The method also includes producing, fortransmission, on the first set of tones a first set of constellationsymbols based upon the bit-loading information. The method also includesproducing a second set of constellation symbols for transmission, wherethere is a difference of n bits between the bit size of the second bitsequence constellation symbol on each tone of the second set of tonesand the bit-loading information associated with each tone of the firstset of tones, and where n is an integer greater than or equal to 0.

BRIEF DESCRIPTION OF THE DRAWINGS

The invention is illustrated by way of example, and not limitation, inthe figures of the accompanying drawings in which like references denotesimilar elements, and in which:

FIG. 1 a illustrates a bundle of cables carrying various types ofsignals as commonly found in a bundle including cables for telephonesignals;

FIG. 1 b illustrates examples of crosstalk in DSL lines;

FIG. 2 a illustrates an I, Q plane for 16-QAM and 4-QAM signalconstellation modulation schemes;

FIG. 3 a illustrates a block diagram of a transmitter chain according toan embodiment;

FIG. 3 b illustrates the digital interface of FIG. 3 a in greater detailin accordance with an embodiment;

FIG. 3 c illustrates a block diagram of a receiver chain according to anembodiment;

FIG. 3 d illustrates in greater detail the digital interface of thereceiver chain of FIG. 3 c according to an embodiment;

FIG. 4 a illustrates the output of a framer according to an embodiment;

FIG. 4 b illustrates an RS codeword according to an embodiment;

FIG. 5 a illustrates a process for changing the mode of operation at thereceiver in reaction to a change in received constellation sizesaccording to an embodiment;

FIG. 5 b illustrates the operation of providing adjusted bit-loadingvalues of FIG. 5 a according to an alternative embodiment of theinvention;

FIG. 5 c illustrates the operation of determining whether adjustedbit-loading values are to be provided of FIG. 5 a in greater detailaccording to an embodiment of the invention;

FIG. 6 a illustrates a process for changing mode and regainingsynchronization after it has been lost according to an embodiment;

FIG. 6 b illustrates the initialization operation of FIG. 6 a in greaterdetail according to an embodiment;

FIG. 6 c illustrates the operation of adjusting the bit stream in orderto regain synchronization of FIG. 6 a in greater detail according to anembodiment of the invention;

FIG. 6 d illustrates the operation of adjusting the bit stream in orderto regain synchronization of FIG. 6 a in greater detail according to anembodiment of the invention;

FIG. 6 e illustrates the operation of adjusting the bit stream in orderto regain synchronization of FIG. 6 a in greater detail according to anembodiment of the invention;

FIG. 6 f illustrates the operation of adjusting the bit stream in orderto regain synchronization of FIG. 6 a in greater detail according to anembodiment of the invention;

FIG. 7 a illustrates a process of regaining synchronization for anoverhead channel which is in a data stream in which OH bytes and CRCbytes are present in a periodic pattern; and

FIG. 7 b illustrates a process of regaining synchronization for anoverhead channel for which OH bytes are replaced with FLAG bytesaccording to an embodiment.

DETAILED DESCRIPTION

According to the invention, methods and apparatus for variable powercommunication including rapid switching between coding constellation ofvarious sizes. In the following description, for purposes ofexplanation, numerous specific details are set forth in order to providea thorough understanding of embodiments according to the invention. Itwill be evident, however, to one of ordinary skill in the art that theinvention may be practiced in a variety of contexts including orthogonalfrequency division modulation systems without these specific details. Inother instances, well-known operations, steps, functions and elementsare not shown in order to avoid obscuring the description.

Parts of the description will be presented using terminology commonlyemployed by those skilled in the art to convey the substance of theirwork to others skilled in the art, such as discrete multi-tone (DMT),constellation, digital subscriber line (DSL), inverse fast Fouriertransform (IFFT), trellis coder or decoder, Reed-Solomon coder ordecoder, convolutional interleaver, and bit-loading among other terms.Various operations will be described as multiple discrete stepsperformed in turn in a manner that is most helpful in understanding thevarious embodiments of the invention. However, the order of descriptionshould not be construed as to imply that these operations arenecessarily performed in the order that they are presented, or evenorder dependent. Repeated usage of the phrases “in an embodiment,” “analternative embodiment,” or an “alternate embodiment” does notnecessarily refer to the same embodiment, although it may. Additionally,one of ordinary skill in the art would appreciate that a graphicaldescription of an apparatus in the figures of the drawingsinterchangeably represents either an apparatus or a method.

A common form of modulation for use with digital subscriber line serviceis discrete multi-tone (DMT) modulation. In DMT modulation, acommunication channel is divided into narrowband sub-channels also oftenreferred to as sub-carriers, bins, or tones. Each of the sub-channels ismodulated by a sub-carrier that is orthogonal to the other sub-carriersallowing for relatively high spectral efficiency. During initializationof a communications link between two modems, the signal-to-noise (SNR)ratio for each of the sub-channels is estimated. The SNR estimateassociated with each sub-channel is then used to set the number of bitseach sub-channel will pass during the time period of a single dataframe. The number of bits assigned to each sub-channel is stored in abit table.

When transmission is occurring on a sub-channel, the bits assigned to asub-channel affect the modulation format used on the sub-channel. Forexample, when 4 bits are assigned to a sub-channel, 16 QAM (quadratureamplitude modulation) may be used to represent the 4 bits during asymbol (also referred to as frame in some cases) time period. The 4 bitscan be represented graphically by a signal point or signal constellationpoint. When 5 bits are assigned to a sub-channel, 32 QAM may be used.

FIG. 2 a illustrates an I, Q plane for 16-QAM and 4-QAM signalconstellation modulation schemes. In FIG. 2 a, for 16-QAM, symbol S₀represents bits ‘0000.’ Symbols S₁ and S₂ represents bits ‘0001’ and‘0010,’ respectively, and so forth up to S₁₅ which represents ‘1111.’The inner 4 symbols S₀, S₅, S₉, S₁₅ of 16-QAM represent symbols S₀, S₁,S₂, S₃, respectively, of 4-QAM.

When the data rate required across a communications link decreasesbecause, for example, a high-data rate application such as (but notlimited to) video is turned off, the transmit data rate and the bitloading on sub-carriers may be decreased. Decreasing the data rate mayresult in a corresponding decreased in the transmit power level whichcan result in a decrease in the crosstalk noise interference to othermodems. When a high data rate is again required, the bit rate andbit-loading can be increased.

FIG. 3 a illustrates a block diagram of a transmitter chain according toan embodiment. Transmitter chain 200 includes transmitter digitalinterface (TDI) 202 which accepts application data from multiple sourcesand supplements it and formats it in a manner suitable for furtherprocessing by byte unpacker (BU) 204. BU 204 disassembles bytes receivedfrom TDI 202 and produces bits that are assigned to particular tonesaccording to tone bit-loading information provided by tone orderer (TO)210. TO 210 receives tone bit-loading information from bit-loading table220 that may be, as described in greater detail below, adjusted bybit-loading adjuster 218 as dictated by control processor 222. In anembodiment, CP 222 sends a 0 bit cutback indication, 1 bit cutbackindication, or 2 bit cutback indication to adjuster 218. Adjuster 218provides tone bit-loading entries from table 220 to TO 210 eitherunadjusted or adjusted according to the cutback indication provided byCP 222. In an embodiment, every two adjacent tones are loaded togetherwith bits, but TO 210 may in an alternative embodiment reorder tonesloaded with 0 bits and 1 bits. In such an embodiment, TO 210 providesthe adjusted and possibly reordered bit-loading table entries of table220 to BU 204 and mapper 206.

In an embodiment, control processor 222 uses network statistics todecide to change the bit loading and the data rate. This may includeexamining the status of packet queues (not shown) or measuring therecent average flow rate of data. The specific mechanism for decidingwhat data rate to use is immaterial to the invention, but rather thatsome mechanism can take advantage of the power cutback scheme describedherein that results in changing the bit-loading on the tones.

Table 1 below illustrates information stored in a bit loading tableaccording to an embodiment. The actual number of bits assigned to aparticular sub-channel are simply illustrative and not limitations ofany particular embodiment. Furthermore, the invention is not limited toany particular value of N, the number of sub-channels (or tones).

TABLE 1 Sub-channel Bits 1 4 2 4 3 5 4 5 5 7 6 8 7 6 8 6 . . . . . . N 4

The output of byte unpacker 204 is provided to constellation mapper (CM)206 which provides each group of bits assigned to a tone a particularamplitude and phase associated with the corresponding constellationsignal point. Trellis coder 208, which is optional, further codes thebits produced by CM 206. If two adjacent tones that are loaded with bitsin tandem by BU 204 can carry a maximum of m and n bits, (m+n−1) bitswill be data bits provided by 204 and the (m+n)^(th) bit is coding bitfrom coder 206. Trellis coders are well known in the art and need not bedescribed further herein.

In an embodiment, the output of tone orderer (TO) 210 is a DMT symbolworth of data that is provided to buffer 212 which is also accessed bygain scaler (GS) 214. GS 214 provides further amplitude adjustment on aper tone basis as specified by gain table 216 so that a specifiedcumulative transmit power level is achieved for all the tones. Theoutput of scaler 214 is provided to a modulator (not shown) which caninclude an inverse fast Fourier transform (IFFT) unit for finaltransmission of the bits to a modem (not shown).

In an embodiment, CP 222 partly controls the operation of TO 210 byinstructing bit-loading adjuster 218 to provide tone bit-loadinginformation from bit-loading table 220 a) unadjusted (i.e., full powermode, FPM), b) with 1 less bit per tone (i.e., 1-bit lower power mode, 1BLPM) or alternatively 2 fewer bits per tone (2-bits lower power mode,2BLPM). If the gain per tone remains constant the use of a smaller sizeconstellation results in a lower transmit power level. CP 222's controlsignal to bit-loading adjuster 218 may indicate that BU 204 andconstellation mapper 206 are to be provided the bit-loading informationfrom table 220 but a) unadjusted (or unmodified), b) reduced by either 1less bit per tone (1-bit lower power mode, 1BLPM), or c) alternatively 2fewer bits per tone (2-bits lower power mode, 2BLPM). For the exampleillustrated by Table 1, BU 204 would put 3 bits on sub-channel 1 if1BLPM was indicated by CP 222 or 2 bits if 2BLPM was indicated by CP222.

In an embodiment, TO 210 handles tones loaded with 0 bits and 1 bitdifferently from the manner for tones which are loaded with 2 or morebits. In an embodiment, TO 210 reorders tones with 0 bits and 1 bit suchthat they are no longer in the order specified by table 220 and,consequently, provides a re-ordered sequence of the bit-loading tableentries before they are passed to constellation mapper 206 and byteunpacker 204. One of ordinary skill in the art would appreciate that inaddition to determining the necessary tone ordering based on theadjusted bit loading table entries as illustrated by the block diagramof FIG. 3 a an alternative embodiment can have several pre-computed toneordering tables stored in memory (not shown) that can be accessed bymapper 206 and unpacker 204 based upon the mode.

As indicated above, the exact condition or conditions that would causeCP 222 to indicate to BU 204 and mapper 206 that they are to change to asmaller size constellations (or from a smaller one to a larger one) areimmaterial to the invention. An example of a condition that wouldtrigger lower power mode operation (i.e., smaller constellation sizeoperation) could be (but is not limited to) the end of a video stream orthe availability of active data for transmission. Furthermore the exactcondition or conditions that would cause CP 222 to indicate to adjuster218 to change the size of the constellation used on each tone isimmaterial to the invention. An example of a condition that wouldtrigger higher power mode operation (i.e., larger constellation sizeoperation) could be (but is not limited to) the start of a video stream.An example of yet another condition that would trigger a change in thepower mode could be receipt of a signal from the receiver specifying achange in the constellation size relative to the constellation sizespecified in bit table 220.

Benefits of simply changing constellation size in order to change thedata rate or transmit power level, include being able to rapidly adaptto changing resource (bandwidth) demands or to quickly modify powertransmit level so as to satisfy the power consumption restrictionsimposed by governmental regulatory agencies without having to utilizeenvironmentally hostile large reductions in signal power. Changingconstellation size entails BU 204 using the per-tone number of bitsspecified by table 220, or 1 bit or 2 bits—depending on the lower powermode (or higher power mode) operation specified by CP 222—less (or more)per tone than specified by bit table 220. This change involves asubtract operation performed on-the-fly and need not be implemented withadditional memory (not shown) storing alternative bit-loading tableswith one less bit per tone or two less bits per tone. However, in analternative embodiment, additional memory stores multiple alternativebit-loading tables with one less bit per tone or two less bits per tonethan specified for the full power bit-loading table.

The invention is not limited to changing the constellation size for allthe active tones. Rather, in an embodiment, the control logic of areceiver, such as receiver 240, can communicate with the control logicof a transmitter, such as transmitter 200, over an administrativechannel and indicate on which tones reduced (or larger) constellationsizes will be used, the allowed values of change in constellation sizerelative to the size specified in bit-loading table 220, or both. In anembodiment, the foregoing tone bit-loading information agreed upon by areceiver and transmitter is stored in memory (not shown) and used by CP222 and adjuster 218 to provide the proper bit-loading information to TO210. The tones which have not been identified as having reduced (orlarger) constellation sizes will be loaded as specified by bit-loadingtable 220. In an alternative embodiment, the control processor of atransmitter, such as transmitter 200, can communicate with the controllogic of a receiver, such as receiver 240 (FIG. 3 c), over anadministrative channel and indicate on which tones reduced (or larger)constellation sizes will be used, the allowed values of change inconstellation size relative to the size specified in bit-loading table220, or both. In such an alternative embodiment, the foregoing tonebit-loading information agreed upon by a transmitter and receiver isstored in memory (not shown) and used by CP 222 and adjuster 218 toprovide the proper bit-loading information to TO 210. The tones whichhave not been identified as potentially having reduced (or larger)constellation sizes will be loaded by mapper 206 as specified bybit-loading table 220 regardless of the power mode.

In an embodiment, the constellation size is changeable on a per DMTsymbol (or DMT frame) basis. A common frame data rate for DSL is 4.059KHz which means that about every 0.25 milliseconds there is anopportunity to change the constellation size if necessary. A DMT symbolrepresents the constellation-encoded bits that are loaded on all thetones and transmitted for about 0.25 milliseconds.

FIG. 3 b illustrates the digital interface (DI) of FIG. 3 a in greaterdetail in accordance with an embodiment. DI 202 includes CRC generator(CRCG) unit 203 a that accepts the output of framer (not shown) thatcollects data from multiple sources and produces a multiplexed dataframe (or muxed data frame). In an embodiment, CRCG unit 203 a insertsoverhead (OH) byte at relatively short periodic intervals. Every SEQP OHbytes a CRC is inserted, where, in an embodiment, SEQP is 68, but othervalues are possible.

FIG. 4 a illustrates the output of a CRC generator and overhead byteinserter according to an embodiment. Data stream 120 includes payloads124, 126 and OH bytes 122. CRC 129 is calculated over all the bytes inpayloads 124, 126 and the bytes in between payloads 124, 126. Scrambler203 b scrambles the output of CRCG 203 a to minimize the possibility ofenormous spikes in amplitude during transmission. Scramblers are wellknown in the art and their presence or absence in an embodiment is notmaterial to the invention, making additional description unnecessary asone of ordinary skill in the art would readily appreciate.

Forward error correction (FEC) coder 203 c is a Reed-Solomon (RS) coderin an embodiment, but other FEC coders are also possible in alternativeembodiments. In an alternative embodiment there may be no RS coder orany type of FEC coder. For every K bytes coder 203 c receives fromscrambler 203 b, coder 203 c adds R check bytes for error correctionsuch that K+R=N_(FEC). Coder 203 c outputs RS codewords with lengthN_(FEC) bytes. In an embodiment, the first byte of an RS codeward is anOH byte or there are no OH bytes in the codeword. In an embodiment, anRS codeword can be up to 255 bytes (N_(FEC)). However, other values ofN_(FEC) are possible and depend on the number of bits in the fundamentalunit of the codeword which, in an embodiment, is an octet, or 8 bits. Ifthe fundamental unit is 8 bits, one can have at most 2⁸−1 bytes in an RScodeword.

FIG. 4 b illustrates a RS codeword according to an embodiment. Codeword130 includes K data bytes and R check bytes for a total of N_(FEC)bytes.

Convolutional interleaver 203 d provides immunity against burst noise byinterleaving the output of coder 203 c across a number of tones andsymbols. Interleaver 203 d has a block size I and a depth D where, in anembodiment, I is equivalent to N_(FEC), and D is chosen such that I andD are mutually prime (i.e., they have no common factors >1). Theinterleaved output sequence for an input x(n) with block length I anddepth D is given as indicated by Eq. 1:Y((n mod I)*D+I*floor(n/I))=x(n)  Eq. 1

Thus, every I^(th) point of x(n) is transmitted without delay, the nextsample is transmitted with a delay of D−1, and the next sample istransmitted with a delay of 2*(D−1), etc . . . The output of interleaver203 d is provided to BU 204. The deinterleaver of the receiver chaindescribed elsewhere herein reverses this process.

FIG. 3 c illustrates a block diagram of a receiver chain according to anembodiment. Receiver chain 240 includes a frequency domain equalizer(FEQ) 254 that accepts a frequency domain representation of the analogsignal received by the analog front end (not shown) and removes thefrequency shaping caused by the communication channel. Equalizer 254outputs “equalized” frequency spectrum data for each received DMT symbolto buffer 252. In an embodiment, the frequency equalized DMT symbol inbuffer 252 has a constant average power output and a specific numericrange of values for each constellation size.

Each DMT symbol in buffer 252 is examined by decision logic (DL) 256 todetermine if the received constellations match the average expectedsize, or if they correspond to a power cutback mode. DL 256 outputs anindication of a cutback by 0 bits (0 bit cutback indication), I bit (1bit cutback indication), or 2 bits (2 bit cutback indication) tobit-loading adjuster 262.

In an embodiment, DL 256 performs the following process in whichmaxcd(n) is a function that takes the absolute value of the maximumtransmitted value for n bits. The process

For tones with n=4 bits or more:

-   if n is even maxcd(n)=2^(n/2)−1-   if n is odd maxcd(n)=2^((n−1)/2*1.5)−1-   For tones with n=0, 1 or 2 bits    -   maxcd(n)=1-   For tones with n=3 bits    -   maxcd(n)=3-   For tones with n>5 bits    -   ½ of the constellation points have        max(abs(Q),abs(I))<=maxcd(n−1)    -   ¼ of the constellation points have        max(abs(Q),abs(I))<=maxcd(n−2)

These formulae are specific to the encoder described in section 7.8.4“Constellation encoder” of standard ITU-T G.992.1. One of ordinary skillin the art would appreciate that other encoders or other constellationtypes would require other formulae and that the invention is not limitedto the formulae provided herein or one type of encoder.

For tones in the set to be used in the decision that have more than 5bits, perform the following processing

-   n1bit=0-   n2bit=0-   for (all tones in set with >5 bits)    -   if (max(abs(Q),abs(I))<(maxcd(n−1)+T)) n1bit=n1bit+1;    -   if (max(abs(Q),abs(I))<(maxcd(n−2)+T)) n2bit=n2bit+1;

If some of the tones to be used in the decision have 5 bits or less,perform the following additional processing. Note thatmaxcd(4)=maxcd(3)=3 and maxcd(0)=maxcd(1)=maxcd(2)=1 so that additionalprocessing is required to distinguish these points.

-   for (all tones in set with 5 bits)    -   if (max(abs(Q),abs(I))<(maxcd(4)+T))n1bit=n1bit+1;    -   if ((max(abs(Q),abs(I))<(maxcd(3)+T)) AND        -   (min(abs(Q),abs(I))<1+T))n2bit=n2bit+1;-   for (all tones in set with 4 bits)    -   if ((max(abs(Q),abs(I))<(maxcd(3)+T)) AND        -   (min(abs(Q),abs(I))<1+T))n1bit=n1bit+1;    -   if (max(abs(Q),abs(I))<(maxcd(2)+T))n2bit=n2bit+1;-   for (all tones in set with 3 bits)    -   if (max(abs(Q),abs(I))<(maxcd(2)+T))n1bit=n1bit+1;    -   if ((max(abs(Q),abs(I))<(maxcd(1)+T)) AND        -   (sign(Q)==sign(I)) n2bit=n2bit+1;-   for (all tones in set with 2 bits)    -   if (sign(Q)==sign(I)) n1bit=n1bit+1;    -   if ((sign(Q)==sign(PRBS(Q)) AND        -   (sign(I)==sign(PRBS(I)))n2bit=n2bit+1;-   for (all tones in set with 1 bit)//Note: 1 bit tones can be used    only if max cutback is limited to 1 bit    -   if ((sign(Q)==sign(PRBS(Q)) AND        -   (sign(I)==sign(PRBS(I)))n1bit=n1bit+1;            T is a decision threshold. In an embodiment, the default            value of T is 1, but other values may yield slight            performance improvements.-   sign( ) refers to the numeric sign of the operand.-   PRBS( ) refers to the recommendation specified constellation value    to assert on a 0 bit tone; for ADSL2, this is specified in section    8.6.3 of standard G.992.3. If there is no distortion or noise in the    signal the decision logic may be-   cutback=0 bits-   if (n1bit==totaltones)cutback=1bits-   if (n2bit==totaltones)cutback=2 bits,    where totaltones is the number of tones examined by the decision    logic.

Assuming that the constellations have been properly randomized by ascrambler of a transmitter such as transmitter 200, the probability thata 0 bit cutback is erroneously recognized as 2 bits of cutback isproportional to 4^(−totaltones). The probability that a 0 bit cutback iserroneously recognized as 1 bit of cutback is proportional to2^(−totaltones)−4^(−totaltones). The total probability of error isproportional to 2^(−totaltones). The probability that a 1 bit cutback iserroneously recognized as 2 bits of cutback is proportional to2^(−totaltones). [Why are the two foregoing error probabilities both2^(−totaltones)?]

In a noiseless condition, there is neither the probability that a 2 bitcutback will be erroneously recognized, nor that a 1 bit cutback will beerroneously recognized as a 0 bit cutback. However, given that noise iscommon in practical implementations the problem of erroneous decisionsis mitigated by implementing the final decision logic as:

-   cutback=0 bits-   if (n1bit==totaltones*T2)cutback=1bits-   if (n2bit==totaltones*T3)cutback=2 bits

T2 and T3 are thresholds that depend on the value of totaltones, the SNRmargin, and the nature of any ‘unpredictable’ but ‘characterizable’noise such as impulses. Values ranging from 0.9 to 1.0 are expected tobe suitable, but any value between 0 and 1 may be appropriate under somecondition. One of ordinary skill in the art would appreciate that T2 andT3 are implementation and operating condition dependent and that theycan be determined without undue experimentation. Furthermore, one ofordinary skill in the art would understand how and be able to extend theabove teachings to produce decision logic that handles more bits ofcutback.

In addition, it would be apparent to one of ordinary skill in the artthat DL 256 may examine the entire set of active tones, or any subset ofthe tones that is sufficiently large. If the cutback determination isused to process the data received on a subset of tones, DL 256, in anembodiment, examines the signal on the tones in that subset.

Depending upon the bit cutback determination made by DL 256, in anembodiment, DL 256 produces a 0 bit cutback indication, 1 bit cutbackindication or a 2 bit cutback indication which DL 256 provides toadjuster 262.

When DL 256 produces a 0 cutback indication, based upon the frequencyordered bit-loading table entries of table 258, DL 256 reverses in theDMT symbol stored in buffer 252 the effect of any ordering performed bya tone orderer such as TO 210. Frequency ordered bit-loading table 258contains entries which indicate the expected bit loading on each of thetones and the order of the tones if they have been reordered by a toneorderer such as TO 210. In an embodiment, CP 260 populates table 258with appropriate entries after an initialization process with atransmitter, such as transmitter 200, is completed. During theinitialization process, the tone bit-loading and active tones arespecified allowing CP 260 to determine which tones would have had theirorder changed by a tone orderer such as TO 210. Tones which would havehad their order changed are identified in the entries in table 258 in amanner allowing TO 250 to undo or reverse in the DMT symbol stored inbuffer 252 the effect of any ordering performed by TO 210.

When DL 256 produces a 1 bit cutback indication or a 2 bit cutbackindication tone deorderer (TDO) 250 determines whether the entries oftable 258 need additional modification to account for the cutbackproducing additional 0 and 1 bit tones that may have required orderingat a transmitter in a manner other than that specified by table 258. IfTDO 250 determines that the additional modification is necessary, TDO250 determines the necessary modifications and based upon themodifications and the entries of table 258 TDO 250 reorders the sequenceof the bit loading entries in table 264 before they are passed on todemapper 246 and byte packer 244. One of ordinary skill in the art wouldappreciate that instead of determining the modifications to the sequenceof bit loading entries in table 264 ‘on-the-fly,’ in an alternativeembodiment tables which reflect the reordered sequences under theconditions of 1 bit cutback or 2 bit cutback are accessible to demapper246 and byte packer 244 and are accessed or selected based on thecutback determination made by DL 256. In an embodiment in which lookuptables are used for both tone ordering and computing the bit loading, itis not necessary to feed the bit loading table values through TO 210 orTDO 250 and such units may be unnecessary in alternative embodiments.

In an embodiment, CP 260 generates and stores configuration parameters,including bit-loading tables 258, 264, selection of tones to use in thecutback determination of DL 256, and selection of the tones that areeligible for cutback (for the case in which CP 260 is part of atransceiver which includes a transmitter). In an embodiment, CP 222performs similar functions using table 220 and a frequency orderedbit-loading table (not shown). Determining the tones suitable forcutback is an implementation detail, but in an embodiment all tones aresuitable for cutback. However, alternative embodiments may limit tonessuitable for cutback to tones that have a certain SNR or havebit-loading above a certain number of bits (e.g., including but notlimited to 4 bits or 6 bits), or a combination of factors including oneor more or none of the foregoing factors. Selecting tones to use in thecutback determination of DL 256 is another implementation detail, but inan embodiment a group of the tones with the largest SNR margin are usedin making the cutback determination. The number of tones to use is animplementation detail that one of ordinary skill in the art would beable to determine without undue experimentation. Alternative embodimentsmay use another criterion, besides SNR margin, or criteria. In anembodiment, an analog front-end (not shown) provides an SNR estimate fortones to CP 260 (or CP 222). In an alternative embodiment, a dedicatedunit operating at baseband using samples from an ADC (not shown)provides SNR estimates for tones to CP 260 (or CP 222).

FIG. 3 d illustrates in greater detail the digital interface of thereceiver chain of FIG. 3 c according to an embodiment. Convolutionalde-interleaver 243 a accepts the output of BPTD 244 and undoes theinterleaving performed by interleaver 203 e at the transmitter toproduce FEC codewords similar to that illustrated in FIG. 4 c. The FECcodewords produced by interleaver 243 a are decoded by FEC decoder 243 band the K error-corrected data bytes of each codeword are provided todescrambler 243 c. Descrambler 243 c undoes the scrambling performed byscrambler 203 c and provides a data stream similar to that shown in FIG.4 b. CRC checksum (CRCC) unit 243 d accepts the output of descrambler243 c, extracts the OH bytes and uses the CRC bytes to perform errordetection before outputting cells similar to the one illustrated in FIG.4 a.

As indicated above, when certain conditions—not material to theinvention—are satisfied, transmitter chain 200 may use constellationsizes (i.e., bit-loading) that is different from what it agreed to witha receiver such as receiver 240 during a synchronization and link setupprocess. In an embodiment, the change in constellation size happenswithout prior agreement with a receiver such as receiver 240. In orderto properly decode the received signals, receiver chain 240 detects thechange in constellation size and makes adjustments to the operation ofreceiver chain 240 to reflect whether there has been a change from 0 bitcutback to 1 bit cutback or 2 bit cutback, whether there has been achange from 1 bit cutback to 2 bit cutback or 0 bit cutback, or whetherthere has been a change from 2 bit cutback to 1 bit cutback or 0 bitcutback. While in an embodiment, after synchronization, datacommunication starts with the transmitter operating in 0 bit cutbackmode, one of ordinary skill in the art would appreciate thatcommunication may, in an alternative embodiment, start in 1 bit cutbackand transition to 0 bit cutback mode or 2 bit cutback. Alternatively,communication may start in 2 bit cutback and transition to 0 bit cutbackor 1 bit cutback.

One of ordinary skill in the art would appreciate that the invention isnot limited to two alternative modes, such as 1 bit cutback and 2 bitcutback, but that the teachings of the disclosure herein can be extendedwithout undue experimentation to additional modes which specify that thebit-loading for tones will be different from the values specified intables 220, 264 by a degree greater than 1 or 2 bits.

FIG. 5 a illustrates a process for changing the mode of operation at thereceiver in reaction to a change in received constellation sizesaccording to an embodiment. In process 500, CP 260 starts 502 byinitializing tables 258, 264 in accordance with link parameters thathave been agreed to between, in an embodiment, a receiver such asreceiver 240 and a transmitter such as transmitter 200. When datacommunication commences and a data symbol arrives at buffer 252, DL 256determines 504 whether adjusted bit-loading values need to be providedto demapper 246 and byte packer 244 via table 264 and adjuster 262. Inan embodiment in which a tone deorderer such as TDO 250 is present, theadjusted bit-loading values are provided to demapper 246 and byte packer244 via TDO 250. In an alternative embodiment, the bit-loading valuesare provided without first passing through a tone deorderer such as TDO250.

In an embodiment, DL 256 employs the pseudo code described elsewhereherein to make the determination whether adjusted bit-loading values areto be provided. Adjusted bit-loading values are to be provided when DL256 determines that the symbol in buffer 252 is indicative of a 1 bitcutback or a 2 bit cutback.

When DL 256 determines that the symbol in buffer 252 is indicative of a0 bit cutback, adjuster 262 provides 508 to TDO 250 bit-loading valuesfrom table 264 without modification. Process 500 then waits 510 foranother symbol to arrive and transitions, when another symbol, arrivesto DL 256 determining 504 again whether adjusted bit-loading values areto be provided.

When DL 256 determines 504 that the symbol in buffer 252 is indicativeof a 1 bit cutback, adjuster 262 provides 506 to TDO 250 bit-loadingvalues from table 264 that have been adjusted to indicate that 1 lessbit is loaded per tone than specified in the corresponding table entryin table 264. Process 500 then waits 510 for another symbol to arriveand transitions, when another symbol, arrives to DL 256 determining 504again whether adjusted bit-loading values are to be provided. When DL256 determines 504 that the symbol in buffer 252 is indicative of a 2bit cutback, adjuster 262 provides 506 to TDO 250 bit-loading valuesfrom table 264 that have been adjusted to indicate that 2 fewer bit areloaded per tone than specified in the corresponding table entry in table264. Process 500 then waits 510 for another symbol to arrive andtransitions, when another symbol, arrives to DL 256 determining 504again whether adjusted bit-loading values are to be provided.

FIG. 5 b illustrates the operation of providing adjusted bit-loadingvalues of FIG. 5 a according to an alternative embodiment of theinvention. As indicated elsewhere herein, a tone orderer and a tonedeorderer are optional. In an embodiment in which a tone orderer ispresent in the transmit chain, a tone deorderer such as TDO 250 undoesat the receiver the ordering performed at transmitter. In an alternativeembodiment, at a receiver, providing 506 adjusted bit-loading valuesincludes determining 507 a whether tone deordering is necessary. Whentone deordering is necessary, adjuster 262 adjusts 507 b, asappropriate, the bit-loading table entries obtained from table 264 andprovides the adjusted bit-loading table entries to TDO 250 fordeordering 507 b as appropriate. TDO 250 provides 507 c the adjusted anddeordered bit-loading values to demapper 246 and byte packer 244.

When tone deordering is unnecessary, adjuster 262 adjusts 507 d, asappropriate, the bit-loading table entries obtained from table 264 andprovides 507 d the adjusted bit-loading table entries to TDO 250 forforwarding to demapper 246 and byte packer 244 without any deordering.

FIG. 5 c illustrates the operation of determining whether adjustedbit-loading values are to be provided of FIG. 5 a in greater detailaccording to an embodiment of the invention. In operation 504 the numberof tones in a symbol in buffer 252 that is indicative of a 1 bit cutbackis determined 505 a, and the number of tones indicative of a 2 bitcutback is determined 505 b. When the total number of tones, totaltones,for which the cutback evaluation is made is the same 505 c as the numberof tones indicative of a 2 bit cutback 505 b, the cutback indication isset to indicate 505 d ‘2 bit cutback.’ When the total number of tones,totaltones, for which the cutback evaluation is made is not the same 505c as the number of tones indicative of a 2 bit cutback 505 b, adetermination 505 e of whether a 1 bit cutback indication is appropriateis made. When the total number of tones, totaltones, for which thecutback evaluation is made 505 e is the same 505 c as the number oftones indicative of a 1 bit cutback 505 a, the cutback indication is setto indicate 505 f ‘1 bit cutback.’ When the total number of tones,totaltones, for which the cutback evaluation is made is not the same 505e as the number of tones indicative of a 1 bit cutback, the cutbackindication is set to indicate 505 g ‘0 bit cutback.’

In the event of an erroneous determination of cutback by DL 250, toomany bits or too few bits are provided to FEC decoder 243 b resulting ina loss of synchronization. A loss of synch signal is produced by FECdecoder 243 b and provided to CP 260. The loss of synch signal isproduced when a certain threshold of ‘bad’ RS codewords is received bydecoder 243 b. The threshold may depend upon, among other factors,interleaver depth, data rate, line condition, etc . . . Setting such athreshold is well known in the art and can be determined by one ofordinary skill in the art without undue experimentation.

In an embodiment, receiver 240 regains RS codeword synchronization byadding bits in the receiver chain before decoder 243 b. One of ordinaryskill in the art would readily appreciate that the teachings of theinvention can be extended to cover regaining codeword resynchronizationfor alternative embodiments that use forward error correction other thanReed-Solomon error correction and that such extensions are encompassedby the invention. Furthermore, one of ordinary skill in the art wouldappreciate that receiver 240 regains RS codeword synchronization byremoving bits from the receiver chain before decoder 243 b.

Consider the case where N_(FEC) is 240 bytes (1920 bits) and that thereare 1180 active tones. A subset of the tones, specifically 1920/2=960tones, are subject to power reduction by 1 bit and only 1 bit cutbackoccurs. Since a RS codeword starts every 1920 bits and any sequence ofpower mode errors results in 960*n bits—where n is an integer—there isonly 1 possible adjustment needed to achieve resynchronization of RSdecoding: adding or, alternatively, removing 960 bits.

While in the foregoing illustrative case, N_(FEC) is 240 bytes (1920bits) and the number of tones is 1180, many other arrangements for RScodeword size and number of tones for which bit loading adjustments canbe specified in any particular implementation of an embodiment, all ofwhich are encompassed by the invention.

Consider the case where N_(FEC) is 240 bytes and there are 1180 activetones. All 1180 tones to be subject to power reduction by 1 or 2 bits.Since 1180 and 1920 have 20 as the greatest common divisor (GCD) thereare a maximum of 1920/20=96 alignment errors possible from any number ofpower mode decision errors. Resynchronization is achieved bysequentially testing 20 bit adjustments in the total bit loading up to96 times. If none of those adjustments achieves synchronization,retraining is performed in an embodiment. When the maximum number ofbits that can be added has been reached, CP 260 and the remainder ofreceiver 240 initiate a retrain process with the transmitter in order toachieve synchronization.

By changing N_(FEC) to 236 bytes where number of tones is 1180, the GCDincreases to 236 and only 8 alignments need to be tested. N_(FEC) canusually be selected in a fairly wide range with little or no performanceconsequences. When the maximum number of bits that can be added (orremoved, depending upon the embodiment) has been reached, CP 260 and theremainder of receiver 240 initiate a retrain process with thetransmitter in order to achieve synchronization.

FIG. 6 a illustrates a process for changing mode and regainingsynchronization after it has been lost according to an embodiment. FIG.6 b illustrates the initialization operation of FIG. 6 a in greaterdetail according to an embodiment. In process 600, CP 260 starts 602 bydetermining a) the greatest common divisor (GCD) 603 a for the number oftones for which cutback is possible (tones_of_cutback) and N_(FEC) interms of bits b) and the number alignments (number_of_alignments=(numberof tones that can be cutback)/GCD) that need to be tested. In anembodiment, during initialization the following expressionGCD(N_(FEC)*8,tones_of_cutback) is maximized in order to minimize thenumber of possible alignments, which is given byN_(FEC)*8/GCD(N_(FEC)*8,tones_of_cutback). Note that ifGCD(N_(FEC)*8,tones_of_cutback)=N_(FEC)*8, only 1 alignment is possibleand no cutback error will cause an FEC SYNC error. CP 260 does notselect values for N_(FEC) that would result in no FEC SYNC error beingproduced when there is a cutback error.

In an embodiment, during the initialization phase of communication witha transmitter which may not be part of process 600 in an alternativeembodiment, for a given number of tones for which cutback is possible CP260 selects a value for N_(FEC) such that the number of alignments(i.e., GCD) is as small as possible without resulting in seriousperformance degradation. The selected value for N_(FEC) is communicatedto the transmitter with which receiver 240 is communicating. In analternative embodiment, the transmitter selects a value of N_(FEC) thatminimizes the number alignments that need to be tested in order toachieve resynchronization and provides that value to CP 260 of receiver240.

While it is preferable to use a GCD number of bits to achieveresynchronization, it is possible in an alternative embodiment to use asmaller value which when multiplied by an integer yields the GCD thatwas calculated for the particular combination of the number of tones andN_(FEC) being used for communication. In an embodiment,bit_adjustment_delta, the number of bits that are added (or removed)from the bit stream is set 603 b by CP 260 to the value of GCD that wascalculated for the particular combination of the number of tones andN_(FEC) being used for communication. An alignment counter,alignment_counter, is initialized 602 to zero.

When loss of synchronization is detected 604 by CP 260, CP 260 makes 606an adjustment to the bit stream reaching decoder 243 b and incrementsalignment_counter. CP 260 then determines 608 whether resynchronizationhas been achieved. In an embodiment, this determination is made by afterCP 260 receives a synchronization signal from decoder 243 b. Whenresynchronization has been achieved, CP 260 stops 614 process 600 andcontinues with other functions. When resynchronization has not beenachieved, CP 260 then determines 610 whether an adjustment limit hasbeen reached by, in an embodiment, determining whether alignment_counteris the same as number_of_alignments, which is the limit on the number ofadjustments that can be made.

When the adjustment limit has been reached, CP 260 initiates 612 aretrain process with the corresponding transmitter in order to regainsynchronization. When the adjustment limit has not been reached, CP 260makes 606 another adjustment to the bit stream.

FIG. 6 c illustrates the operation of adjusting the bit stream in orderto regain synchronization of FIG. 6 a in greater detail according to anembodiment of the invention. In an embodiment, CP 260 adds 607 a ‘faketones,’ at the beginning or the end of table 264, that total the numberof desired bits and asserting a constellation value of Q=I=1 for theadded tones. Some Viterbi decoders (e.g., Wei's 4D decoder) known in theart run in data order and allow an even number of Q=I=1 constellationsto be inserted at the beginning or end of the DMT symbol withoutinducing errors in the remainder of the signal. Decoders are describedin paragraph 8.6.2 of standard ITU G.992.3.

In an embodiment, CP 260 adds ‘fake tones’ for the duration of one DMTsymbol at a time. In other words, CP 260 removes 607 b the added faketones at the conclusion of the processing of the bits of the DMT symbolfor which ‘fake tones’ were added. CP 260 checks 608 for asynchronization indication from decoder 243 b. If no synchronizationindication is received within a certain period of time that isimplementation dependent, CP 260 adds ‘fake tones’ for another DMTsymbol. The foregoing process is repeated until resynchronization isachieved or the limit on bits that can be added has been reached.

FIG. 6 d illustrates the operation of adjusting the bit stream in orderto regain synchronization of FIG. 6 a in greater detail according to anembodiment of the invention. FIG. 6 e illustrates the operation ofadjusting the bit stream in order to regain synchronization of FIG. 6 ain greater detail according to an embodiment of the invention. In analternative embodiment, bit_adjustment_delta bits can also be added 609or, alternatively, removed 611 by byte packer 244. In such alternativeembodiments, byte packer 244 accepts from CP 260 an indication of thenumber of bits to be added or removed. BP 244 may then insert bits thatwere erroneously not supplied by demapper 246 or remove bits that wereerroneously supplied by demapper 246.

FIG. 6 f illustrates the operation of adjusting the bit stream in orderto regain synchronization of FIG. 6 a in greater detail according to anembodiment of the invention. In an alternative embodiment, thebit-loading table operates normally with additional fake tones thatresult in bit_adjustment_delta bits being added for each DMT symbol. Theadditional bits are ignored by the remainder of the receive chain.However, when a loss of synchronization occurs the fake tones areselectively removed 613 for subsequently received symbols untilresynchronization reoccurs or a retraining is necessary.

Referring again to FIG. 4 b, data stream 120 also represents the outputof data scrambler 243 c. When an improper mode change occurs a loss ofsynchronization also happens at CRC checksum unit 243 d causing unit 243d to be unable to distinguish OH bytes from CRC or payload bytes and forthe OH bytes to be extracted and decoded to create the received OHchannel.

Techniques for regaining synchronization in the OH channel include: 1)restricting overhead byte insertion to a simple periodic pattern andusing a hunting algorithm for proper CRC to detect the CRC byte; 2)having a receiver indicate to the transmitter that synchronization hasbeen lost so that the transmitter will transmit a FLAG byte continuouslyinstead of an OH byte and having the transmitter transmit only a FLAGbyte until instructed otherwise by the receiver.

With regards to the first technique, in an embodiment, control processor260 uses the linearity property of the CRC of two sequences to quicklyidentify a CRC byte in the sequence of bytes produced by descrambler 243c.

Let B1=(B11x^((N−1))+B21x^((N−2)) . . . ) where N is a DSL mux dataframe. DSL mux data frames can be identified by CRC unit 243 d becausethey start at the beginning of RS codewords. LetC1=(B1x^((N(M−1)))+B2x^((N(M−2)))+ . . . ) be a complete overhead framewhere M=seqp*Tp. If CRC(Bn) is known, it is possible to compute CRC(C)as CRC(C1)+CRC(C2)=CRC(B1x^(N(M−1)))+CRC(B2x^(N(M−2)))+ . . . whereC2=B₂x^(N(M−1))+B3^(N(M−2))+ . . . ButCRC(B1x^(N(M−1)))=CRC(B1x^(N(M−2)))x^(8N) mod g(x). Now Qx^(8N) mod g(x)can be found quickly with a pre-computed lookup table (LUT) stored inmemory 266. Thus, by recursion CRC(C1)= . . .LUT(LUT(LUT(CRC(B1))+CRC(B2))+ . . . ) where LUT indicates that a LUToperation is to be performed with the value in between the parentheses () as the argument or index into the LUT. This algorithm is iterated overrelatively large blocks of data so that the LUT recursion is a fastcomputation. This allows computation of CRC(Cy) for many alignments veryquickly. In addition, only the values of CRC(By) need to be stored totest many alignments.

FIG. 7 a illustrates a process of regaining synchronization for anoverhead channel which is in a data stream in which OH bytes and CRCbytes are present in a periodic pattern. In process 700, controlprocessor 260 does a sliding window CRC computation and computes 702 theCRC of (B1 B2 . . . BN) by the LUT table method described elsewhereherein. Using the described efficient recalculation technique for theCRC of a sliding window of N bytes, control processor 260 compares 704the CRC of a certain N sequential bytes to the (N+₁)^(st) byte. Controlprocessor 260 determines whether the CRC of a certain N sequential bytesis equivalent 706 to the (N+1)^(st) byte. When the computed CRC for thecertain N sequential bytes is not equivalent to the (N+1)^(st) byte,control processor 260 advances 708 the N-byte-long window by 1 byte.When the computed CRC for the certain N sequential bytes is equivalentto the (N+₁)^(st) byte, control processor 260 indicates 710 to CRCchecksum unit 243 d where the OH bytes can be found in data stream 120of FIG. 4 b. CRC checksum unit 243 d is then able to do a CRC check onthe bytes it receives from descrambler 243 c and produce 712 OH bytesfor the overhead channel.

FIG. 7 b illustrates a process of regaining synchronization for anoverhead channel for which OH bytes are replaced with FLAG bytesaccording to an embodiment. With regards to the second technique forregaining synchronization for the OH and CRC bytes at the output ofdescrambler 243 c, control processor 260 communicates to a transmittersuch as transmitter 200 through an administration channel thatsynchronization has been lost 722. Control logic 216 of transmitter 200,in response to receiving a loss of synchronization signal, transmits,instead of OH bytes, FLAG bytes that are received 724 by controlprocessor 260. Control processor 260 then searches 726 for the FLAG bytethat should appear periodically at overhead byte locations 122. Oncecontrol processor 260 finds the FLAG bytes in the overhead channel itindicates 728 to CRC checksum unit and OH byte extractor 243 d thelocation of the FLAG bytes so that OH byte extractor 243 d issynchronized with the pattern of OH and CRC bytes that will resume.Control processor 260 also instructs transmitter 200 thatsynchronization in the OH channel has been achieved and that transmitter200 can resume transmitting 730 OH bytes and CRC bytes. In analternative embodiment, transmitter 200 transmits FLAG bytes for apredetermined fixed time period and then resumes transmitting OH bytesand CRC bytes. In such an alternative embodiment, transmitter 200 doesnot depend upon control processor 260 to indicate that synchronizationin the OH channel has been achieved.

In an alternative embodiment, transmitter 200 transmits FLAG bytes for apredetermined fixed time period and then resumes transmitting OH bytesand CRC bytes. In such an alternative embodiment, transmitter 200 doesnot depend upon control processor 260 to indicate that synchronizationin the OH channel has been achieved. If, after a fixed time period,control processor 260 is unable to detect FLAG bytes after indicatingthat synchronization has been lost to transmitter 200, control processor260 indicates again to transmitter 200 that synchronization in the OHchannel has been lost.

In the preceding specification, the invention has been described withreference to specific exemplary embodiments of the invention. It will,however, be evident to one of ordinary skill in the art that variousmodifications and changes be made without departing from the broaderspirit and scope of the invention as set forth in the claims thatfollow. The specification and drawings are accordingly to be regarded inan illustrative rather than restrictive sense and the intention is notto be limited to the details given herein, but rather to be modifiedwithin the scope of the appended claims along with their full scope ofequivalents. The various elements or components described herein may becombined or integrated in another system or certain features may beomitted, or not implemented.

1. A method of receiving a transmitter signal with varying power, themethod comprising: providing bit-loading information for each tone ofmultiple tones, wherein the multiple tones include a first set of tonesand a second set of tones; receiving for each tone of the first set oftones a first bit sequence constellation symbol, wherein there is adifference of m bits between the bit size of the first bit sequenceconstellation symbol on each tone of the first set of tones and thebit-loading information associated with each tone of the first set oftones; producing, based upon the first bit sequence constellation symbolon each tone of the first set of tones, off of each tone of the firstset of tones bits to generate a first bit sequence, wherein there is thedifference of m bits between the bits produced off each tone of thefirst set of tones and the bit-loading information associated with eachtone of the first set of tones, and m is an integer greater than orequal to 0; receiving for each tone of a second set of tones a secondbit sequence constellation symbol; determining, for the second set oftones on each of which a second bit sequence constellation symbol isreceived, a cutback indication; determining that the cutback indicationis indicative of a difference of n bits between the bit size of thesecond bit sequence constellation symbol on each tone of the second setof tones and the bit-loading information associated with each tone ofthe second set of tones; producing, based upon 1) the second bitsequence constellation symbol on each tone of the second set of tones,2) the value of n, and 3) the bit loading information associated witheach tone of the second set of tones, off of each tone of the second setof tones bits to generate a second bit sequence, wherein there is thedifference of n bits between the bits produced off of each tone of thesecond set of tones and the bit-loading information associated with eachtone of the second set of tones, and n is an integer greater than orequal to 0 and m is not equal to n.
 2. The method of claim 1, whereinthe value of n is greater than the value of m.
 3. The method of claim 1,wherein the value of n is less than the value of m.
 4. The method ofclaim 3, wherein the value of n is defined by sending to a transmitter asignal to change power mode.
 5. The method of claim 1, wherein the firstset of tones includes the second set of tones and the second set oftones has fewer tones than the first set of tones, further comprisingsending to a transmitter an indication specifying which tones of themultiple tones are among the second set of tones.
 6. The method of claim1, wherein the first set of tones has the same number of tones as themultiple tones.
 7. The method of claim 6, wherein the second set oftones has a fraction of the number of tones that the first set of toneshas.
 8. The method of claim 1, wherein m is 0 and n is
 2. 9. The methodof claim 1, wherein m is 2 and n is
 0. 10. The method of claim 1,wherein m is 1 and n is
 0. 11. The method of claim 1, wherein m is 0 andn is
 1. 12. An apparatus for receiving a transmitter signal with varyingpower, the apparatus comprising: a bit-loading table providingbit-loading information for each tone of multiple tones, wherein themultiple tones include a first set of tones and a second set of tones; aconstellation de-mapper that is to receive for each tone of the firstset of tones a first bit sequence constellation symbol, wherein there isa difference of m bits between the bit size of the first bit sequenceconstellation symbol on each tone of the first set of tones and thebit-loading information associated with each tone of the first set oftones, and the constellation de-mapper is to produce, based upon thefirst bit sequence constellation symbol on each tone of the first set oftones, bits to be produced off of each tone of the first set of tones; areceiver front-end that is to receive for each tone of a second set oftones a second bit sequence constellation symbol; decision logic is todetermine, for the second set of tones on each of which a second bitsequence constellation symbol is received, a cutback indication, and isto determine that the cutback indication is indicative of a differenceof n bits between the bit size of the second bit sequence constellationsymbol on each tone of the second set of tones and the bit-loadinginformation associated with each tone of the second set of tones;wherein the constellation de-mapper is to produce, based upon a) thesecond bit sequence constellation symbol on each tone of the second setof tones, b) the value of n, and c) the bit loading informationassociated with each tone of the second set of tones, bits to beproduced off of each tone of the second set of tones to generate asecond bit sequence, wherein there is the difference of n bits betweenthe bits produced off of each tone of the second set of tones and thebit-loading information associated with each tone of the second set oftones, and n is an integer greater than or equal to 0 and m is not equalto n.